July 2000
ML4875*
Low Voltage Boost Regulator with Shutdown
GENERAL DESCRIPTION
The ML4875 is a boost regulator designed for DC to DC
conversion in 1 to 3 cell battery powered systems. The
combination of BiCMOS process technology, internal
synchronous rectification, variable frequency operation,
and low supply current make the ML4875 ideal for 1 cell
applications. The ML4875 is capable of start-up with input
voltages as low as 1V and is available in 5V, 3.3V, and 3V
output versions with an output voltage accuracy of ±3%.
Unlike regulators using external Schottky diodes, the
ML4875 isolates the load from the battery when the
SHDN pin is high. This is accomplished by an integrated
synchronous rectifier which eliminates the need for an
external Schottky diode and provides a lower forward
voltage drop, resulting in higher conversion efficiency. In
addition, low quiescent battery current and variable
frequency operation result in high efficiency even at light
loads. The ML4875 requires only one inductor and two
capacitors to build a very small regulator circuit capable
of achieving conversion efficiencies in excess of 90%.
The circuit contains a
RESET
output which goes low when
the DETECT input drops below 200mV.
FEATURES
s
s
s
s
s
s
s
Guaranteed start-up and operation at 1V input
Pulse Frequency Modulation and Internal Synchronous
Rectification for high efficiency
Isolates the load from the input during shutdown
Minimum external components
Low ON resistance internal switching FETs
Micropower operation
5V, 3.3V, and 3V output versions
*Some Packages Are End Of Life Or Obsolete
BLOCK DIAGRAM
L1
V
OUT
PWR
GND
8
V
L
6
5
V
OUT
V
IN
1
FEEDBACK
*C
IN
V
BAT
BOOST
CONTROL
C
OUT
GND
3
REGULATION
&
SHUTDOWN
CONTROL
REF
+
–
SHDN
2
DETECT
4
*R
A
RESET
7
FROM POWER
MANAGEMENT
*R
B
5V
*Optional
1
ML4875
ABSOLUTE MAXIMUM RATINGS
Absolute maximum ratings are those values beyond which
the device could be permanently damaged. Absolute
maximum ratings are stress ratings only and functional
device operation is not implied.
V
OUT ................................................................................................
7V
Voltage on any other pin ...... GND – 0.3V to V
OUT
+ 0.3V
Peak Switch Current, I
(PEAK) .................................................
1.5A
Average Switch Current, I
(AVG) .......................................
300mA
Junction Temperature ............................................. 150°C
Storage Temperature Range ...................... –65°C to 150°C
Lead Temperature (Soldering 10 sec.) ..................... 260°C
Thermal Resistance (q
JA
) Plastic SOIC ................. 160°C/W
OPERATING CONDITIONS
Temperature Range
ML4875CS-X .............................................. 0°C to 70°C
ML4875ES-X ........................................... –20°C to 70°C
V
IN
Operating Range
ML4875CS-X ................................. 1.0V to V
OUT
–0.2V
ML4875ES-X .................................. 1.1V to V
OUT
–0.2V
ELECTRICAL CHARACTERISTICS
Unless otherwise specified, V
IN
= Operating Voltage Range, T
A
= Operating Temperature Range (Note 1).
PARAMETER
SUPPLY
V
IN
Current
V
IN
= V
OUT
– 0.2V
V
IN
= 4.8V, SHDN = V
IN
V
OUT
Quiescent Current
V
L
Quiescent Current
PFM REGULATOR
Pulse Width (T
ON
)
Output Voltage (V
OUT
)
ML4875-5
ML4875-3
ML4875-T
Load Regulation
ML4875-5
ML4875-3
ML4875-T
Under-Voltage Lockout Threshold
SHUTDOWN
Input Bias Current
Shutdown Threshold
Shutdown Hysteresis
RESET
COMPARATOR
DETECT Threshold
DETECT Bias Current
RESET
ON Voltage
RESET
OFF Current
Note 1:
CONDITIONS
MIN
TYP.
MAX
UNITS
50
20
8
65
30
12
1
µA
µA
µA
µA
8.9
T
ON
= 0 at V
OUT
(MAX),
8.9µs - T
ON
- 11.1µs V
OUT
(MIN)
See Figure 1
V
IN
= 1.2V, I
OUT
- 20mA
V
IN
= 2.4V, I
OUT
- 100mA
V
IN
= 1.2V, I
OUT
- 30mA
V
IN
= 2.4V, I
OUT
- 140mA
V
IN
= 1.2V, I
OUT
- 35mA
V
IN
= 2.4V, I
OUT
- 160mA
4.85
3.2
2.91
4.85
4.85
3.2
3.2
2.91
2.91
10
5.0
3.3
3.0
5.0
5.0
3.3
3.3
3.0
3.0
0.85
11.1
5.15
3.4
3.09
5.15
5.15
3.4
3.4
3.09
3.09
1
µs
V
V
V
V
V
V
V
V
V
V
–100
V
SHDN
= high to low
180
200
50
100
220
70
nA
mV
mV
194
–100
I
RESET
= 50µA
V
RESET
= 5V
200
206
100
mV
nA
mV
µA
100
200
1
Limits are guaranteed by 100% testing, sampling or correlation with worst case test conditions.
3
ML4875
FUNCTIONAL DESCRIPTION
The ML4875 combines Pulse Frequency Modulation
(PFM) and synchronous rectification to create a boost
converter that is both highly efficient and simple to use.
A PFM regulator charges a single inductor for a fixed
period of time and then completely discharges before
another cycle begins, simplifying the design by
eliminating the need for conventional current limiting
circuitry. Synchronous rectification is accomplished by
replacing an external Schottky diode with an on-chip
PMOS device, reducing switching losses and external
component count.
REGULATOR OPERATION
A block diagram of the boost converter is shown in Figure
2. The circuit remains idle when V
OUT
is at or above the
desired output voltage, drawing 50µA from V
IN
, and 8µA
from V
OUT
through the feedback resistors R1 and R2.
When V
OUT
drops below the desired output level, the
output of amplifier A1 goes high, signaling the regulator to
deliver charge to the output. Since the output of amplifier
A2 is normally high, the flip-flop captures the A1 set signal
and creates a pulse at the gate of the NMOS transistor Q1.
The NMOS transistor will charge the inductor L1 for 10µs,
resulting in a peak current given by:
SHUTDOWN
The ML4875 output can be shut down by pulling the
SHDN pin high. When SHDN is high, the regulator stops
switching, the control circuitry is powered down, and the
body diode of the PMOS synchronous rectifier is
disconnected from the output, allowing the output voltage
to drop below the input voltage. This feature is unique to
the ML4875, as most boost regulators use external
Schottky diode rectifier which cannot be disconnected
during shutdown. Leaving the Schottky diode connected
causes excess power dissipation in the load during
shutdown because the Schottky conducts whenever the
output voltage drops 300mV below the input voltage.
RESET
COMPARATOR
An additional comparator is provided to detect low V
IN
,
or any other error condition that is important to the user.
The inverting input of the comparator is internally
connected to V
REF
, while the non-inverting input is
provided externally at the DETECT pin. The output of the
comparator is the
RESET
pin, which swings from V
OUT
to
GND when an error is detected.
DESIGN CONSIDERATIONS
INDUCTOR
Selecting the proper inductor for a specific application
usually involves a trade-off between efficiency and
maximum output current. Choosing too high a value will
keep the regulator from delivering the required output
current under worst case conditions. Choosing too low a
value causes efficiency to suffer. It is necessary to know
the maximum required output current and the input
voltage range to select the proper inductor value. The
maximum inductor value can be estimated using the
following formula:
V
×
T
ON(MIN)
× η
L
MAX
=
IN(MIN)
2
×
V
OUT
×
I
OUT(MAX)
2
I
L(PEAK)
=
T
ON
×
V
IN
10µs
×
V
IN
≈
L
1
L
1
(1)
For reliable operation, L1 should be chosen so that I
L(PEAK)
does not exceed 1.5A.
When the one-shot times out, the NMOS transistor
releases the V
L
pin, allowing the inductor to fly-back and
momentarily charge the output through the body diode of
PMOS transistor Q2 in series with shutdown transistor Q3.
But, as the voltage across the PMOS transistor changes
polarity, its gate will be driven low by the current sense
amplifier A2, causing Q2 to short out its body diode. The
inductor then discharges into the load through Q2. The
output of A2 also serves to reset the flip-flop and one-shot
in preparation for the next charging cycle. A2 releases the
gate of Q2 when its current falls to zero. If V
OUT
is still
low, the flip-flop will immediately initiate another pulse.
The output capacitor (C1) filters the inductor current,
limiting output voltage ripple. Inductor current and one-
shot waveforms are shown in Figure 3.
(2)
where
h
is the efficiency, typically between 0.8 and 0.9.
Note that this is the value of inductance that just barely
delivers the required output current under worst case
conditions. A lower value may be required to cover
inductor tolerance, the effect of lower peak inductor
currents caused by resistive losses, and minimum dead
time between pulses.
Another method of determining the appropriate inductor
value is to make an estimate based on the typical
performance curves given in Figures 4 and 5. Figure 4
shows maximum output current as a function of input
voltage for several inductor values. These are typical
performance curves and leave no margin for inductance
and ON-time variations. To accommodate worst case
conditions, it is necessary to derate these curves by at
least 10% in addition to inductor tolerance.
For example, a two cell to 5V application requires 80mA
of output current while using an inductor with 15%
tolerance. The output current should be derated by 25%
to 100mA to cover the combined inductor and ON-time
INDUCTOR
CURRENT
Q(ONE SHOT)
Q1 ON
Q1 & Q2 OFF
Q2
ON
Q1 ON
Q2
ON
Figure 3. PFM Inductor Current Waveforms and Timing.
5
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